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1 of 22 optimum technology matching? applied gaas hbt ingap hbt gaas mesfet sige bicmos si bicmos sige hbt gaas phemt si cmos si bjt gan hemt functional block diagram rf micro devices?, rfmd?, optimum technology matching?, enabling wireless connectivity?, powerstar?, polaris? total radio? and ultimateblue? are trademarks of rfmd, llc. bluetooth is a trade- mark owned by bluetooth sig, inc., u.s.a. and licensed for use by rfmd. all other trade names, trademarks and registered tradem arks are the property of their respective owners. ?2006, rf micro devices, inc. product description 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . ordering information prescaler 32/64 phase detector & charge pump lock detect loop flt 14 16 div ctrl dc bias 5 tx out 2 osc e 1 osc b 15 ld flt mod in 8 resntr+ 13 resntr- 12 3pd rf2516 vhf/uhf transmiiter the rf2516 is a monolithic integrated circuit intended for use as a low- cost am/ask transmitter. the device is provided in a 16-pin qsop-16 package and is designed to provide a phased locked frequency source for use in local oscillator or transmitter applications. the chip can be used in applications in the north american and european vhf/uhf bands. the integrated vco, phase detector, prescaler, and reference oscillator transis- tor require only the addition of an external crystal to provide a complete phase-locked loop. in addition to th e standard power-down mode, the chip also includes an automatic lock-detect feature that disables the transmit- ter output when the pll is out-of-lock. features ? fully integrated pll circuit ? integrated vco and refer- ence oscillator ? 2.25v to 3.6v supply voltage ? low current and power down capability ? 100mhz to 500mhz fre- quency range ? out-of-lock inhibit circuit applications ? 315/433mhz band systems ? local oscillator source ? part 15.231 applications ? remote keyless entry ? wireless security systems ? am/ask/ook transmitter rf2516 vhf/uhf transmiiter RF2516PCBA-410 fully assembled evaluation board rev a17 ds060712 9 rf2516 vhf/uhf transmiiter rohs compliant & pb-free product package style: ssop-16
2 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . absolute maximum ratings parameter rating unit supply voltage -0.5 to +3.6 v dc power down voltage (v pd ) -0.5 to v cc v mod in -0.5 to 1.1 v operating ambient temperature -40 to +85 c storage temperature -40 to +150 c parameter specification unit condition min. typ. max. overall t=25c, v cc =2.8v, freq=433mhz, r modin =3k frequency range 100 to 500 mhz modulation am/ask modulation frequency 1 mhz incidental fm 15 khz p-p output power +8.5 +10 dbm 50 load on/off ratio 75 db pll and prescaler prescaler divide ratio 32/64 vco gain, k vco 20 mhz/v frequency and board layout dependent. pll phase noise -97 dbc/hz 10khz offset, 50khz loop bandwidth -102 dbc/hz 100khz offset, 50khz loop bandwidth harmonics -60 dbc with output tuning. reference frequency 17 mhz crystal frequency spurs -50 dbc 50khz pll loop bandwidth max crystal r s tbd 35 50 for a typ. 1ms turn-on time. max crystal motional inductance 60 mh for a typ. 1ms turn-on time. charge pump current 100 ak pd =100 a/2 =0.0159ma/rad power down control power down ?on? v cc -0.3v v voltage supplied to the input; device is ?on? power down ?off? +0.3 v voltage supplied to the input; device is ?off? control input impedance 100k turn on time 1 2 ms crystal start-up, 13.57734mhz crystal. turn off time 1 2 ms power supply voltage 2.8 v specifications 2.25 3.6 v operating limits current consumption (avg.) 6 10.5 ma 50% duty cycle 10khz data applied to the mod in input. r modin (r10)=3k . output power/dc current consumption externally adjustable by modulation input resistor (see applicable application schematic). power down current 0 1 ua pd =0v, mod in=0v, div ctrl=0v caution! esd sensitive device. exceeding any one or a combination of the absolute maximum rating conditions may cause permanent damage to the device. extended application of absolute maximum rating conditions to the device may reduce device reliability. specified typical perfor- mance or functional operation of the devi ce under absolute maximum rating condi- tions is not implied. rohs status based on eudirective2002/95/ec (at time of this document revision). the information in this publication is believed to be accurate and reliable. however, no responsibility is assumed by rf micro devices, inc. ("rfmd") for its use, nor for any infringement of patents, or other rights of third parties, resulting from its use. no license is granted by implication or otherwise under any patent or patent rights of rfmd. rfmd reserves the right to change component circuitry, recommended appli- cation circuitry and specifications at any time without prior notice.
3 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . pin function description interface schematic 1osc b this pin is connected directly to the reference oscillator transistor base. the intended reference oscillator configuration is a modified colpitts. a 68pf capacitor should be connected between pin 1 and pin 2. 2osc e this pin is connected directly to the emitter of the reference oscillator tran- sistor. a 33pf capacitor should be connected from this pin to ground. see pin 1. 3pd power down control for all circuitry. when this pin is a logic ?low? all circuits are turned off. when this pin is a logic ?high?, all circuits are operating nor- mally. a ?high? is v cc . diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 4gnd ground connection for the tx out amp. keep traces physically short and connect immediately to ground plane for best performance. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) pro- tection using the human body model. 5txout transmitter output. this output is an open collector and requires a pull-up inductor for bias/mat ching and a tapped capacitor for matching. 6gnd1 ground connection for the tx output buffer amplifier. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 7vcc1 this pin is used to supply bias to the tx buffer amplifier. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protec- tion using the human body model. 8mod in am analog or digital modulation can be imparted to the carrier by an input to this pin. an external resistor is used to bias the output amplifiers through this pin. the voltage at this pin must not exceed 1.1v. higher voltages may damage the device. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 9vcc2 this pin is used to supply dc bias to the vco, crystal oscillator, pre-scaler, phase detector, and charge pump. an if bypass capacitor should be con- nected directly to this pin and returned to ground. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. see pin 7. 10 gnd2 digital pll ground connection. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. osc e v cc osc b v cc pd tx ou t mod in rf in vcc1 v cc 1 k mod in tx ou t v cc gnd v cc
4 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . pin function description interface schematic 11 vref p bias voltage reference pin for bypassing. the bypass capacitor should be of appropriate size to provide filtering of the reference crystal frequency and be connected directly to this pin. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 12 resntr- the resntr pins are used to supply dc voltage to the vco, as well as to tune the center frequency of the vco. equal value inductors should be con- nected to this pin and pin 13. 13 resntr+ see pin 12. 14 loop flt output of the charge pump. an rc network from this pin to ground is used to establish the pll bandwidth. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. 15 ld flt this pin is used to set the threshold of the lock-detect circuit. a shunt capacitor should be used to set an rc time constant with the on-chip series 1k resistor. this signal is used to clamp (enable or disable) the mod in circuitry. the time constant should be approximately 10 times the refer- ence period. diodes shown in the interface schematic provide 3kv electro- static discharge (esd) protecti on using the human body model. 16 div ctrl logic ?high? input select s divide-by-64 prescaler. logic ?low? input selects divide-by-32 prescaler. diodes shown in the interface schematic provide 3kv electrostatic discharge (esd) protection using the human body model. vref p v cc resntr- resntr+ loop flt 4 k loop fl t v cc v cc ld flt 1 k v cc div ctrl
5 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . package drawing 0.157 0.150 0.196 0.189 0.2440 0.2284 0.0688 0.0532 0.050 0.016 0.0098 0.0075 8 max 0min notes: 1. shaded lead is pin 1. 2. all dimensions are excluding mold flash. 3. lead coplanarity - 0.005 with respect to datum "a". 0.012 0.008 0.025 -a- 0.0098 0.0040
6 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . rf2516 theory of operation introduction short range radio devices are becoming commonplace in toda y?s environment. the most common examples are the remote keyless entry systems popular on many new cars and trucks, an d the ubiquitous garage door opener. other applications are emerging with the growth in home security, automation and the advent of various remote control applications. typically these devices have been simplex, or one-way, links. they are also ty pically built using surface acoustic wave (saw) devices as the fr e- quency control elements. this approach has been attractive be cause the saw devices have been readily available and a trans- mitter, for example, could be built with only a few additional co mponents. recently however, rf micro devices, inc. (rfmd), has introduced several new components that enable a new class of short-range radio devices based on the use of crystals and phase-locked loops for frequency control. these devices are superi or in performance and comparable in cost to the traditional saw-based designs. the rf2516 is an example of such a device. the rf2516 is targeted for applications such as 315mhz and 433mhz band remote keyless entry systems and wireless secu rity systems, as well as other remote control applications. the rf2516 transmitter the rf2516 is a low-cost am/ask vhf/uhf transmitter design ed for applications operating within the frequency range of 100mhz to 500mhz. in particular, it is intended for 315mhz to 433mhz band systems, remote keyless entry systems, and fcc part 15.231 periodic transmitters. it can also be used as a local oscillator signal source. the integrated vco, phase detec - tor, prescaler, and reference oscillator require only the addition of an external crystal to provide a complete phase-locked lo op. in addition to the standard power-down mode, the chip also in cludes an automatic lock-detect feature that disables the trans- mitter output when the pll is out-of-lock. the device is manufactured on a 25ghz silicon bipolar-cmos pr ocess and packaged in an industry standard ssop-16 plastic package. this, combined with the low external parts count, enab les the designer to achieve small-footprint, high-performance, low-cost designs. the rf2516 is designed to operate from a supply voltage ra nging from 2.25v to 3.6v, accommodating designs using three nicd battery cells, two aaa flashlight cells, or a lithium button battery. the device is capable of providing up to +10dbm outp ut power into a 50 load, and is intended to comply with fcc requiremen ts for unlicensed remote control transmitters. esd pro- tection is provided on all pins except vco and tx out. while this device is intended for ook oper ation, it is possible to use narrowband fm. this is accomplished by modulating the reference oscillator rather than applying the data to the mod in input pin. the mod in pin should be tied high to cause the device to transmit. the deviation will be set by pulling limits of the crystal. deviation sufficient for the transmission of vo ice and other low data rate signals can therefore be accomplished. refe r to the application schematic in the data sheet for details. the rf2516 functional blocks a pll consists of a reference oscillator, a phase detector, a l oop filter, a voltage controlled oscillator (vco), and a program ma- ble divider in the feedback path. the rf2516 includes all of th ese internally, except for the loop filter and the reference osc illa- tor?s crystal and two feedback capacitors. the reference oscillator is a colpitts type oscillator. pins 1 (osc b) and 2 (osc e) provide connections to a transistor that is used as the reference oscillator. the colpit ts configuration is a low parts count topology with reliable performance and reason - able phase noise. alternatively, an external signal could be in jected into the base of the transistor. the drive level should, in either case, be around 500mv pp . this level prevents overdriving the device and keeps the phase noise and reference spurs to a minimum. the prescaler divides the vco frequency by either 64 or 32, using a seri es of flip-flops, depending upon the logic level present at the div ctrl pin. a high logic level will select the 64 divi sor. a low logic level will select the 32 divisor. this divided signal is then fed into the phase detector where it is compared with the reference frequency.
7 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . the rf2516 contains an onboard phase detector and charge pump. the phase detector compares the phase of the reference oscillator to the phase of the vco. the phase detector is implemented using flip-flops in a topology referred to as either ?dig ital phase/frequency detector? or ?digital tri-state comparator?. the circuit consists of two d flip-flops whose outputs are combine d with a nand gate which is then tied to the reset on each flip-f lop. the outputs of the flip-flops are also connected to the cha rge pump. each flip-flop output signal is a series of pulses whose frequency is related to the flip-flop input frequency. when both inputs of the flip-flops are id entical, the signals are both frequency- an d phase-locked. if they are different, they will provide signals to the charge pump which will either charge or discharge the loop filter, or enter into a high impedance state. the name ?tri-state comparator? comes from this. the main benefit of this type of detector is the ability to co rrect for errors in both phase an d frequency. when locked, the de tec- tor uses phase error for correction. when unlocked, it uses freque ncy error for correction. this type of detector will lock und er all conditions. the charge pump consists of two transistors, one for charging the loop filter and the other for discharging the loop filter. its inputs are the outputs of the phase detector flip-flops. since there are two flip-flops, there are four possible states. if bot h amplifier inputs are low, then the amplifier pair goes into a hi gh impedance state, maintaining the charge on the loop filter. the state where both inputs are high will not occur. the other states are either charging or discharging the loop filter. the loop filter integrates the pulses coming from the charge pump to cr eate a control voltage for the voltage controlled oscillator. the vco is a tuned differential amplifier with the bases and colle ctors cross-coupled to provide positive feedback and a 360 phase shift. the tuned circuit is located in the collectors, and is comprised of internal varactors and external inductors. the designer selects the inductors for the desired frequency of op eration. these inductors also provide dc bias for the vco. the output of the vco is buffered and applied to the prescaler ci rcuit, where it is divided by either 32 or 64, as selected by the designer, and compared to the reference oscillator frequency. the transmit amplifier is a two-stage amplifier consisting of a driver and an open collector final stage. it is capable of providing 10dbm of output power into a 50 load while operating from a 3.6v power supply. the lock-detect circuitry connects to the output of the ph ase detector circuitry and is used to disable the transmitter when the vco is not phase-locked to the reference os cillator. this is necessary to avoid unwanted out-of-band transmission and to pro- vide compliance with regulatory li mits during an unlocked condition. there are many possible reasons for the pll not to be locked. for instance, there is a short period during the start of any vco in which the vco begins oscillating and the reference oscillator bu ilds up to full amplitude. during this period, the frequency will likely be outside the authorized band. typically, the vco st arts much faster than the reference oscillator. once both vco and reference oscillators are running, the phase detector can st art slewing the vco to the correct frequency, slowly sliding across 200mhz of occupied spectrum. in competitive devices, the vco radiates at full power under all of these conditions. the lock protection circuit in the rf2516 is intended to stabil ize quickly after power is applied to the chip, and to disable t he base drive to the transmit amplifier. this attenuates the output to levels that will be generally acceptable to regulatory boar ds as spurious emissions. once the phase detector has locked the oscillators, then the lock circuit enables the mod in pin for transmission of the desired data. there is no need for an extern al microprocessor to monitor the lock status, although that can be done with a low current a/d converter in a system micro, if needed. the lock-detect circuitry contains an internal resistor which, combined with a designer-chosen capacitor for a particular rc time constant, filters the lock-detect signal. this signal is then passed through an internal schmitt trigger and used to enable or disable the transmit amplifier. if the oscillator unlocks, even momentarily, the protection circ uit quickly disables the output until the lock is stable. these unlocks can be caused by low battery voltage, poor power supply regulation, severe shock of the crystal or vco, antenna load- ing, component failure, or a myriad of unexpected single-point failures. the rf2516 contains onboard band gap referenc e voltage circuitry which provides a stable dc bias over varying temperature and supply voltages. additionally, the device features a power-down mode, eliminating battery disconnect switches.
8 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . designing with the rf2516 the reference oscillator is built around the onboard transistor at pins 1 and 2. the intended topology is that of a colpitts oscil- lator. the colpitts oscillator is quite common and requires few ex ternal components, making it ideal for low-cost solutions. th e topology of this type of oscillator is as seen in the following figure. this type of oscillator is a parallel resonant circuit for a fund amental mode crystal. the transistor amplifier is an emitter f ol- lower and the voltage gain is developed by the tapped capa citor impedance transformer. the series combination of c 1 and c 2 act in parallel with the input capacitance of the transistor to capacitively load the crystal. the nominal capacitor values can be ca lculated with the following equations 6 : and the load capacitance is usually 32pf. the variable freq is th e oscillator frequency in mhz. the frequency can be adjusted by either changing c 2 or by placing a variable capacitor in series with th e crystal. as an example, assume a desired frequency of 14mhz and a load capacitance of 32pf. c 1 =137.1pf and c 2 =41.7pf. these capacitor values provide a starting point. the drive level of the oscillator should be checked by looking at the signal a t pin 2 (osc e). it has been found that the leve l at this pin should generally be around 500mv pp or less. this will reduce the ref- erence spur levels and reduce noise from distortion. if this level is higher than 500mv pp then increase the value of c 1 . the val- ues of these capacitors are usually tweaked during design to m eet performance goals, such as minimizing the start-up time. additionally, by placing a variable capacitor in series with the crystal, one is able to adjust the frequency. this will also a lter the drive level, so it should be checked again. an important part of the overall design is the voltage controlled oscillator . the vco is configured as a differential amplifier. the vco is tuned via internal varactors. the varactors are tuned by the loop filter output voltage through a 4k resistor. x1 c2 c1 v cc c 1 60 c load ? freq mhz ----------------------- - = c 2 1 1 c load ------------- 1 c 1 ------ ? -------------------------- =
9 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . as mentioned earlier, the inductors and the varactors are tuning a differential amplifier. to tune the vco the designer only needs to calculate the value of the inductors connected to pins 12 and 13 (resntr- and resntr+). the inductor value is determined by the equation: in this equation, f is the desired operating frequency and l is the value of the inductor required. the value c is the amount of capacitance presented by the varactors and parasitics. for calcul ation purposes 1.5pf should be used. the factor of one-half is due to the inductors being in each leg. as an example, a ssume an operating frequency of 433mhz. the calculated value of each inductor is 45nh. a 47nh inductor would be appropriate as the closest available value. the setup of the vco can be summarized as follows. first, open the loop. next, get the vco to run on the desired frequency by selecting the proper inductor and capacitor values. the capacitor value will need to include the varactor and circuit parasitic s. after the vco is running at the desired frequency, set the vco se nsitivity. the sensitivity is de termined by connecting the con - trol voltage input point to ground and noting the frequency. connect the same point to the supply, and again note the freq uency. the difference between these two frequencies divided by the supply voltage is the vco sensitivity expressed in hz/v. incr easing the inductor value while decreasing the capacitor value will increase the sensitivity. decreasing the inductor value while increasing the capacitor value will lower the sensitivity. when increasing or decreasing component values, make sure th at the center frequency remains constant. finally, close the loop. external to the part, the designer needs to implement a loop filter to complete the pll. the loop filter converts the output of the charge pump into a voltage that is us ed to control the vco. internally, the vco is connected to the charge pump output through a 4k resistor. the loop filter is then connected in parallel to this point at pin 14 (loop flt). this limits the loop filter topology to a second order filter usually consisting of a shun t capacitor and a shunt series rc. a passive filter is most commo n, as it is a low-cost and low-noise design. an additional pole coul d be used for reducing the reference spurs, however there is n ot a way to add the series resistor. however, this should not be a reason for concern. 4 k loop flt l l resntr+ resntr- l 1 2 f ?? ---------------- ?? ?? 2 1 c --- - 1 2 -- - ?? =
10 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . the schematic of the loop filter is: the transfer function is: where the time constants are defined as: and the frequency at which unity gain occurs is given by: this is also the loop bandwidth. if the phase margin (pm) and the loop bandwidth ( lbw ) are known, it is possible to calculate the time constants. these are found using the equations 4 : and 4 k loop flt l l resntr+ resntr- fs () r 2 s 2 1 + ? s 2 s 1 1 ) + ? ( ?? ------------------------------------------- ? = 2 r 2 c 2 ? = 1 r 2 c 1 c 2 ? c 1 c 2 + ------------------- ? ? ? ? ? = lbw 1 1 2 ? ------------------ - = 1 pm () sec pm () tan ? lbw -------------------------------------------------- = 2 1 lbw 2 1 ? ----------------------- - =
11 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . with these known, it is then possible to determine the values of the filter components. 4 as an example, consider a loop bandwidth of 50khz, a phase margin of 45, a divide ratio of 64, a k vco of 20mhz/v, and a kpd of 100 a/2 rad. time constant 1 is 1.31848 s, time constant 2 is 7.68468 s, c 1 is 20.9pf, c 2 is 100.8pf, and r 2 is 76.2 k . in order to perform these calculations, one will need to know the value of two constants, k vco and k pd . k pd is calculated by dividing the charge pump current by 2 . for the rf2516, the charge pump current is 100 a. k vco is best found empirically as it will change with frequency and board parasitics. by briefly co nnecting pin 14 (loop flt) to vcc and then to ground, the fre- quency tuning range of the vco can be s een. dividing the difference between these two frequencies by the difference in the voltage gives k vco in mhz/v. the control lines provide an interface for connecting the device to a microcontrolle r or other signal generating mechanism. the designer can treat pin 8 (mod in), pin 16 (div ctrl), and pin 3 (pd) as control pins whose voltage level can be set. the lock- detect voltage at pin 15 (ld flt) is an output that can be monitored by the microcontroller. pin 15 (ld flt) is used to set the threshold of the lock-detect circuit . a shunt capacitor is used to set an rc time constant with an on-chip series 1k resistor. the time constant should be approximately 10 times the reference period. general rf bypassing techniques must be observed to get the best perf ormance. choose capacitors such that they are series resonant near the frequency of operation. board layout is always an area in which great care must be taken. the board material and thickness are used in calculating the rf line widths. the use of vias for connection to the ground plane allows one to connect to ground as close as possible to ground pins. when laying out the traces around the vco, it is desirable to keep the parasitics equal between the two legs. this will allow equal valued inductors to be used. pre-compliance testing should be performed during the design process. th is can be done with a gtem cell or at a compliance testing laboratory. it is recommended that pre-compliance test ing be performed so that there are no surprises during final compliance testing. this will help keep the product development and release on schedule. working with a laboratory offers the benefit of years of compliance testing experience and familiarity with the regulatory issues. also, the laboratory can often provide feedback that will help the designer make the product compliant. on the other hand, having a gtem cell or an open air test site locally offers the designer the ability to rapidly determine whether or not design changes impact the product's compliance. se t-up of an open air test site and the associated calibration is not trivial. an alternative is to use a gtem test cell. after the design has been completed and passes compliance testin g, application will need to be made with the respective reg- ulatory bodies for the geographic region in which the pr oduct will be operated to obtain final certifications. c 1 1 2 ---- - k pd k vco ? lbw 2 n ? ----------------------------- 1 lbw 2 ? () 2 + 1 lbw 1 ? () 2 + ---------------------------------------- ?? = c 2 c 1 2 1 ---- -1 ? ?? ?? ? = r 2 2 c 2 ------ =
12 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . rf2516 typical applications fcc part 15.231 periodic transmitter - 315mhz automotive keyless entry transmitter the following information is taken or paraphrased from the code of federal regulations title 47, part 15, section 231 (47 cfr 15.231). part 15 discusses radio frequency devices and section 231 discusses periodic transmissi ons. please refer to the reg- ulation itself as the final authority. additional info rmation may be found on the internet at www.fcc.gov. to highlight the main guidelines outlined by this section, ther e are five main limitations: oper ating frequency, transmission c on- tent, transmission duration, emission bandwidth, and spurious emissions. part 15.231 allows operation in two bands: 40.66mhz to 40.70 mhz and above 70mhz. transmissi on is limited to control sig- nals such as alarm systems, door openers, remote switches, etc. radio control of toys is not permitted, nor is continuous trans - mission such as voice or video. data transmission other than a recognition code is not permitted. transmission time is limited to 5 seconds (paragraph a) or for 1 second with greater than ten seconds off (paragraph e). emission bandwidth between 70mhz and 900mhz can not be more than 0.25% of the center frequency. above 900mhz, the emission bandwidth cannot be greater than 0.50% of the center frequency. the emission bandwidth is determined from the points that are 20db down from the modulated carrier. this corr esponds to an occupied bandwidt h of 4.5mhz at a center fre- quency of 902mhz, 1.1mhz at 433mhz, and 788khz at 315mhz. spurious emissions limits are listed in tabular form for vari ous frequency ranges in the section 231. above 470mhz with a manually activated transmitter, the fundamental field strength at a distance of 3 meters shall not exceed 12,500microvolts/meter. the spurious emissions shall not ex ceed 1,250microvolt/meter at a distance of 3meters above 470mhz. refer to appendix a for a method of converting field strength to power. in the frequency range of 260mhz to 470mhz, one needs to line arly interpolate the maximum emissions level for both the fun- damental and spurious emissions. the equation for this line is given by: this equation is derived from the endpoints of the frequency ra nge and their respective field st rengths. note that the field strength is in microvolts per meter and the frequency is in mega hertz. to determine the spurious level, divide the level calcu- lated above for the spurious frequency by ten. as an example, assume the fundamental is 315mhz and the re ference frequency is 9.8 mhz. th e field strengths of the funda- mental, the reference spurs, and the harmon ics of the fundamental up through the tenth harmonic are calculated in the follow- ing table the occupied bandwidth limit is 787.5khz. as shown in table a, the fifth, seventh, and ninth harmonics fall into restricted bands as called out in section 15.205. the limits fo r these restricted bands are called out in section 15.209. the power level in the last column is the level if the output is co nnected directly to a spectrum analyzer. refer to appendix a as to how this column was calculated. local oscillator source since the rf2516 has a phase-locked vco, it can be used as a signal source. the device is an ask/ook transmitter, with the data provided at the mod in pin. when the mod in is a high logi c level, the carrier is transmitted. when mod in is a low logic level, then the carrier is not transmitted. therefore, to use th e rf2516 as signal source, simply tie the mod in pin to the sup ply voltage, through a suitable series resistor (minimum 3k ). e v m ------- 41 2 3 -- - freq mhz 7083 1 3 -- - ? ? =
13 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . conclusions the rf2516 is an am/ook vhf/uhf transmitter that features a ph ase-locked output. this device is suitable for use in a cfr part 15.231 compliant product as well as a local oscillator si gnal source. two examples showing these applications were dis- cussed. the rf2516 is packaged in a low-cost plastic package and requir es few external parts, thus making it suitable for low-cost designs. table a frequency (mhz) 15.205 limits ( v/m@3m) 15.231 limits ( v/m@3m) final fcc mask ( v/m@3m) final fcc mask ( v/m@3m) power level (dbm, 50 ) ref spur 305.2 - 604.17 604.17 55.62 -39.61 1 315.0 - 6041.67 6041.67 75.62 -19.61 ref spur 324.8 - 604.17 604.17 55.62 -39.61 2 630.0 - 604.17 604.17 55.62 -39.61 3 945.0 - 604.17 604.17 55.62 -39.61 4 1260.0 - 604.17 604.17 55.62 -39.61 5 1575.0 500 - 500.00 53.98 -41.25 6 1890.0 - 604.17 604.17 55.62 -39.61 7 2205.0 500 - 500.00 53.98 -41.25 8 2520.0 - 604.17 604.17 55.62 -39.61 9 2835.0 500 - 500.00 53.98 -41.25 10 3150.0 - 604.17 604.17 55.62 -39.61
14 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . pin out 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 div ctr l ld flt loop fl t resntr + resntr - vrefp gnd2 vcc2 osc b osc e pd gnd tx out gnd1 vcc1 mod in
15 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . application schematic 315mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 68 pf 9.83 mhz 33pf *not populated on standard evaluation board. osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip 4 pf 50 strip 56 nh 16 k j1 tx out 220 pf 10 tx vcc 100 pf mod in s1 cas-120b 10 82 nh 82 nh 2 k 10 nf 4.3 k 2.2 nf 1 nf v c c v c c v c c pd
16 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . application schematic 315mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 68 pf 9.83 mhz 33pf osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip 4 pf 50 strip 56 nh 16 k j1 tx out 220 pf 10 tx vcc 100 pf s1 cas-120b 10 82 nh 82 nh 2 k 10 nf 4.3 k 2.2 nf 1 nf pd d1 smv1249-011 150 k audio v cc v cc rf2516 audio transmitter v cc v cc
17 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . application schematic 433mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 68 pf 13.57734 mhz pwr dwn 4.3 k 220 pf 220 pf 10 nf 220 pf div ctr 10 nf tx out 33pf 1 nf 2.2 nf 39 nh 2 k 10 10 nf *not populated on standard evaluation board. * 2.8 v cc (v) mod. in res. value (r5) i cc (ma) p out (dbm) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k 17.38 10.51 8.68 7.82 7.18 6.75 6.45 6.18 5.99 5.80 5.66 7.45 8.78 7.23 6.00 4.73 3.81 2.98 2.30 1.63 1.00 0.35 2.0 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k i cc (ma) 11.08 10.83 4.61 4.00 3.63 3.42 3.26 3.15 3.07 3.01 2.95 p out (dbm) -6.23 -4.40 -5.61 -6.66 -8.08 -8.93 -10.04 -10.71 -11.58 -12.32 -13.10 2.4 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k i cc (ma) 14.05 9.00 7.48 6.73 6.16 5.79 5.53 5.29 5.13 4.98 4.86 p out (dbm) 7.94 7.63 5.95 4.64 3.35 2.40 1.47 0.75 0.05 -0.60 -1.26 3.2 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k p out (dbm) 6.77 9.70 8.30 7.11 5.91 5.02 4.16 3.51 2.89 2.26 1.66 i cc (ma) 20.90 12.12 9.66 8.95 8.23 7.75 7.42 7.10 6.89 6.68 6.52 3.6 v cc (v) mod. in res. value (r5) 1k 3k 5k 7k 9k 11k 13k 15k 17k 19k 21k p out (dbm) 5.78 10.42 9.18 8.08 6.88 6.02 5.19 4.52 3.93 3.35 2.72 i cc (ma) 24.68 13.88 10.94 10.14 9.34 8.81 8.44 8.09 7.86 7.63 7.44 osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip 4 pf 50 strip 68 nh 2 pf 50 strip 15 pf 10 nh 15 pf 10 nh 22 nh 220 pf 10 nf 220 pf 10 nf 10 3 k 10 nf mod in 39 nh v cc v cc v cc pd
18 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . evaluation board schematic 315mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 c8 68 pf y1 9.83 mhz c7 33pf *not populated on standard evaluation board. osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip c6 4 pf 50 strip l3 56 nh r4 16 k j1 tx out c5 220 pf tx vcc c4 100 pf mod in s1 cas-120b r2 10 l2 82 nh l1 82 nh r1 2 k c1 1 f r3 4.3 k c2 2.2 nf c3 1 nf vcc vcc vcc gnd p1-1 vcc1 p1-3 mod in p1 1 2 3 con3 b1 lith batt vcc + - 2516400, rev a pd r5 10
19 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . evaluation board schematic 433mhz 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 c2 68 pf x1 13.57734 mhz pwr dwn r2 4.3k c7 220 pf c9 220 pf c10 10 nf vcc c12 220 pf div ctrl c11 10 nf c1 33pf c6 1 nf c8 2.2 nf l2 39 nh r4 2k r3 10 c13 10 nf *not populated on standard evaluation board. c17* osc b osc e gnd tx out gnd1 vcc1 mod in div ctrl ld flt loop flt resntr+ resntr- vrefp gnd2 vcc2 50 strip c3 4 pf 50 strip l4 68 nh c15 2 pf 50 strip c14 15 pf l3 10 nh c16 15 pf l5 10 nh l6 22 nh c18 220 pf c19 10 nf vcc c5 220 pf c4 10 nf r1 10 vcc r5 3k c20 10 nf l1 39 nh j1 tx out j2 mod in p1 1 2 3 con3 vcc nc gnd p2 1 2 3 con3 div ctrl gnd pwr dwn pd
20 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . evaluation board layout (315mhz) board size 1.285? x 1.018? board thickness 0.062?, board material fr-4
21 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . evaluation board layout (433mhz) board size 1.392? x 0.813? board thickness 0.062?, board material fr-4
22 of 22 rf2516 rev a17 ds060712 7628 thorndike road, greensboro, nc 27409-9421 for sales or technical support, contact rfmd at (+1) 336-678-5570 or sales-support@rfmd.com . 433mhz phase noise 0 1.0 1.0 -1.0 10.0 1 0 . 0 - 1 0 . 0 5.0 5 . 0 - 5 . 0 2.0 2 . 0 - 2 . 0 3.0 3 . 0 - 3 . 0 4.0 4 . 0 - 4 . 0 0.2 0 . 2 - 0 . 2 0.4 0 . 4 - 0 . 4 0.6 0 . 6 - 0 . 6 0.8 0 . 8 - 0 . 8 rf2516 output z swp max 1ghz swp min 0.1ghz vcc = 3 v vcc = 2 v vcc = 3.3 v 1.0 ghz 0.1 ghz

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